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AD603AR-REEL7 Scheda tecnica(PDF) 4 Page - Analog Devices |
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AD603AR-REEL7 Scheda tecnica(HTML) 4 Page - Analog Devices |
4 / 14 page REV. C –4– AD603 THEORY OF OPERATION The AD603 comprises a fixed-gain amplifier, preceded by a broadband passive attenuator of 0 dB to 42.14 dB, having a gain-control scaling factor of 40 dB per volt. The fixed gain is laser-trimmed in two ranges, to either 31.07 dB ( ×35.8) or 50 dB ( ×358), or may be set to any range in between using one external resistor between Pins 5 and 7. Somewhat higher gain can be obtained by connecting the resistor from Pin 5 to com- mon, but the increase in output offset voltage limits the maximum gain to about 60 dB. For any given range, the band- width is independent of the voltage-controlled gain. This system provides an under- and overrange of 1.07 dB in all cases; for example, the overall gain is –11.07 dB to 31.07 dB in the maximum-bandwidth mode (Pin 5 and Pin 7 strapped). This X-AMP structure has many advantages over former methods of gain-control based on nonlinear elements. Most importantly, the fixed-gain amplifier can use negative feedback to increase its accuracy. Since large inputs are first attenuated, the amplifier input is always small. For example, to deliver a ±1 V output in the –1 dB/+41 dB mode (that is, using a fixed amplifier gain of 41.07 dB) its input is only 8.84 mV; thus the distortion can be very low. Equally important, the small-signal gain and phase response, and thus the pulse response, are essentially indepen- dent of gain. Figure 1 is a simplified schematic. The input attenuator is a seven-section R-2R ladder network, using untrimmed resistors of nominally R = 62.5 Ω, which results in a characteristic resis- tance of 125 Ω ± 20%. A shunt resistor is included at the input and laser trimmed to establish a more exact input resistance of 100 Ω ± 3%, which ensures accurate operation (gain and HP corner frequency) when used in conjunction with external resistors or capacitors. The nominal maximum signal at input VINP is 1 V rms ( ±1.4 V peak) when using the recommended ±5 V supplies, although operation to ±2 V peak is permissible with some increase in HF distortion and feedthrough. Pin 4 (SIGNAL COMMON) must be connected directly to the input ground; significant impedance in this connection will reduce the gain accuracy. The signal applied at the input of the ladder network is attenu- ated by 6.02 dB by each section; thus, the attenuation to each of the taps is progressively 0 dB, 6.02 dB, 12.04 dB, 18.06 dB, 24.08 dB, 30.1 dB, 36.12 dB and 42.14 dB. A unique circuit technique is employed to interpolate between these tap-points, indicated by the “slider” in Figure 1, thus providing continuous attenuation from 0 dB to 42.14 dB. It will help, in understanding the AD603, to think in terms of a mechanical means for moving this slider from left to right; in fact, its “position” is controlled by the voltage between Pins 1 and 2. The details of the gain- control interface are discussed later. The gain is at all times very exactly determined, and a linear-in- dB relationship is automatically guaranteed by the exponential nature of the attenuation in the ladder network (the X-AMP principle). In practice, the gain deviates slightly from the ideal law, by about ±0.2 dB peak (see, for example, Figure 16). Noise Performance An important advantage of the X-AMP is its superior noise per- formance. The nominal resistance seen at inner tap points is 41.7 Ω (one third of 125 Ω), which exhibits a Johnson noise- spectral density (NSD) of 0.83 nV/ √Hz (that is, √4kTR) at 27°C, which is a large fraction of the total input noise. The first stage of the amplifier contributes a further 1 nV/ √Hz, for a total input noise of 1.3 nV/ √Hz. It will be apparent that it is essential to use a low resistance in the ladder network to achieve the very low specified noise level. The signal’s source impedance forms a voltage divider with the AD603’s 100 Ω input resistance. In some applications, the resulting attenuation may be unaccept- able, requiring the use of an external buffer or preamplifier to match a high impedance source to the low impedance AD603. The noise at maximum gain (that is, at the 0 dB tap) depends on whether the input is short-circuited or open-circuited: when shorted, the minimum NSD of slightly over 1 nV/ √Hz is achieved; when open, the resistance of 100 Ω looking into the first tap generates 1.29 nV/ √Hz, so the noise increases to a total of 1.63 nV/ √Hz. (This last calculation would be important if the AD603 were preceded by, for example, a 900 Ω resistor to allow operation from inputs up to 10 V rms.) As the selected tap moves away from the input, the dependence of the noise on source impedance quickly diminishes. Apart from the small variations just discussed, the signal-to- noise (S/N) ratio at the output is essentially independent of the attenuator setting. For example, on the –11 dB/+31 dB range the fixed gain of ×35.8 raises the output NSD to 46.5 nV/√Hz. Thus, for the maximum undistorted output of 1 V rms and a 1 MHz bandwidth, the output S/N ratio would be 86.6 dB, that is, 20 log (1 V/46.5 µV). SCALING REFERENCE VG GAIN CONTROL INTERFACE AD603 PRECISION PASSIVE INPUT ATTENUATOR FIXED GAIN AMPLIFIER *NORMAL VALUES R = 2R LADDER NETWORK VPOS VNEG GPOS GNEG VINP COMM 0dB –6.02dB –12.04dB –18.06dB –24.08dB –30.1dB –36.12dB –42.14dB RR RR R R R 2R 2R 2R 2R 2R 2R R 20 * 694 * 6.44k * VOUT FDBK Figure 1. Simplified Block Diagram of the AD603 |
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